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| High Voltage Power Switching Regulator The MC33369 through MC33374 are monolithic high voltage power switching regulators that combine the required converter functions with a unique programmable state controller, allowing a simple and economical powersystem solution for office automation, consumer, and industrial products. These devices are designed to operate directly from a rectified AC line source, and in flyback converter applications are capable of providing an output power in excess of 150 W with a fixed AC input of 100 V, 115 V, or 230 V, and in excess of 90 W with a variable AC input that ranges from 85 V to 265 V. This device series features a programmable state controller, an on-chip 700 V SENSEFETTM power switch circuit, 700 V active off-line startup circuit including a high voltage JFET and a low voltage MOSFET, auto restart logic, fixed frequency duty cycle controlled oscillator, current limiting comparator with leading edge blanking, latching pulse width modulator for double pulse suppression, and a high gain amplifier with a bandgap reference. Protective features include cycle-by-cycle current limiting, input undervoltage lockout with hysteresis, and a non-latching thermal shutdown. These devices are available in economical 8-pin dual-in-line and five pin TO-220 style packages. * Programmable State Controller MC33369 thru MC33374 Order this document by MC33370/D HIGH VOLTAGE OFF-LINE POWER SWITCHING REGULATOR SEMICONDUCTOR TECHNICAL DATA P SUFFIX PLASTIC PACKAGE CASE 626 8 1 5. Power Switch Pin 6. Ground 7. Ground 8. Ground Pin 1. VCC 2. Feedback Input 3. Ground 4. State Control Input T SUFFIX PLASTIC PACKAGE CASE 314D 1 5 * * * * * * * * On-Chip 700 V SENSEFET Power Switch Circuit Rectified AC Line Source Operation from 85 V to 265 V On-Chip 700 V Active Off-Line Start-Up Circuit Latching PWM for Double Pulse Suppression Cycle-By-Cycle Current Limiting Input Undervoltage Lockout with Hysteresis Non-Latching Internal Thermal Shutdown Enhanced Functionality Over TOP200 and TOP221 Series Typical Application + AC Input Aux Power Supply Feedback VCC 1 Programmable State Controller Feedback Input 2 + Pulse Width Modulator Controller Startup Circuit Snubber + + DC Output Device + TV SUFFIX PLASTIC PACKAGE CASE 314E 1 5 Pin 1. VCC 2. Feedback Input 3. Ground 4. State Control Input 5. Power Switch Pin Heatsink surface connected to Pin 3 ORDERING INFORMATION Power Switch Circuit On Peak Resistance Current (A) (W) 12 12 6.8 4.8 4.0 12 12 6.8 4.8 3.8 3.0 12 12 6.8 4.8 3.8 3.0 0.5 0.9 1.5 2.0 2.5 0.5 0.9 1.5 2.0 2.7 3.3 0.5 0.9 1.5 2.0 2.7 3.3 Package 5 Power Switch Pin - MC33369P MC33370P MC33371P MC33372P MC33373AP MC33369T MC33370T MC33371T MC33372T MC33373T MC33374T MC33369TV MC33370TV MC33371TV MC33372TV MC33373TV MC33374TV (c) Motorola, Inc. 1999 Plastic DIP-8 State Control Input 4 Power Switch Circuit On/Off Straight Lead Ground 3 Vertical Mount This device contains 391 active transistors. Rev 3 MOTOROLA ANALOG IC DEVICE DATA 1 MC33369 thru MC33374 MAXIMUM RATINGS AA AAAA A A A A AAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A AAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A AAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAA AAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAA A A A A AAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A AAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A AAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AA AA AAAAAAAAAAAAAAAAAAAAAAA AA A A A AA A AA A AAAAAAAAAAAAAAAAAAAAAAA A AA AA AAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAA A AA AAAAAAAAAAAAAAAAAAAAAA A A AA AAAAAAAAAAAAAAAAAAAAAA A A AA AAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAA AA A A AAAAAAAAAAAAAAAAAAAAAAA AA A A A AA A AA AA AAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAA AA A A AAAAAAAAAAAAAAAAAAAAAAA AA A A A AA A AA AA AAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAA A AA AA AAAAAAAAAAAAAAAAAAAAAAA Power Switch and Start-Up Circuit (Pin 5) Voltage Range Pin 5 Current Peak During Transformer Saturation Power Supply Voltage Range (Pin 1) Feedback Input (Pin 2) Voltage Range Current State Control Input Current (Pin 4) V5 I5(pk) VCC -0.3 to 700 2.0 Ilim Max -0.3 to 10 -0.3 to 10 100 50 V A V VIR(fb) Ifb Ist V mA mA Thermal Characteristics P Suffix, Plastic Package Case 626 Junction-to-Lead Junction-to-Air, 2.0 oz. printed circuit copper clad 0.36 sq. inch 1.0 sq. inch T and TV Suffix, Plastic Package Case 314 Junction-to-Case Junction-to-Air Operating Junction Temperature Storage Temperature C/W RJC RJA 5.0 45 35 2.0 65 Characteristic Symbol fOSC OSCILLATOR Frequency (Ifb = 4.0 mA) TJ = 25C TJ = Tlow to Thigh AMPLIFIER and PWM COMPARATOR (Pin 2) Feedback Input Shunt Regulation (Ifb = 4.0 mA, TJ = Tlow to Thigh) Voltage Voltage Temperature Coefficient Feedback Input (Ifb = 3.5 mA to 4.5 mA) Resistance (TJ = 25C) Resistance Temperature Coefficient (TJ = Tlow to Thigh) Feedback Input Current at Threshold of Duty Cycle Reduction MC33369, MC33370 MC33371 MC33372 MC33373A, MC33373 MC33374 Amplifier/PWM Gain (Ifb = 3.5 mA to 4.5 mA) Gain (TJ = 25C) Gain Temperature Coefficient (TJ = Tlow to Thigh) Rating Symbol Value Unit TJ -40 to +150 C Tstg -65 to +150 C ELECTRICAL CHARACTERISTICS (Pin 1 connected to Pin 2, for typical values TJ = 25C, for min/max values TJ is the operating junction temperature range that applies (Note 2), unless otherwise noted.) Min Typ Max Unit kHz 90 70 100 - 110 115 DVreg(fb) DRI RI Vreg(fb) 8.3 - 14 - 8.6 0.005 19 0.3 8.9 - 23 - V %/C W %/C mA Ith(PWM) 1.2 1.3 1.4 1.5 1.6 1.6 1.8 2.0 2.1 2.2 2.1 2.3 2.4 3.0 3.2 DAV AV -10 - 71 0.5 -14 -0.05 74 0.9 -18 - 77 2.0 %/mA %/C % PWM Duty Cycle Maximum (Ifb = ICC1) Minimum (Ifb = 10 mA) SHUTDOWN LATCH External Shutdown Activation, Current into Pin 2 to Set Latch Power-Up Reset Threshold, Pin 1 Voltage to Reset Latch STATE CONTROL (Pin 4) Input Open Circuit Voltage (Ifb = 4.0 mA) Set Comparator (VCC = Vreg(fb)) Threshold Voltage Input Clamp Voltage (Iin = 0.5 mA) Input Clamp Current (Vin = 8.6 V) Toggle Comparator (VCC = Vreg(fb)) Threshold Voltage (Vin Decreasing) Hysteresis (Vin Increasing) Input Current (Vin = 0.2 V) Input Reset Current (VCC < Vrst, Vst = 1.1 V) D(max) D(min) Isd Vrst 30 2.5 3.2 4.1 5.0 - 1.6 - - 1.0 70 3.7 150 5.0 3.8 4.7 6.5 - 2.0 - - 7.0 mA V V Voc(st) 3.55 4.4 5.5 1.0 Vth(st) Vclmp(st) Iin(st) Vth(tg) VH(tg) Iin(tog) Irst(st) V V mA 1.8 200 -40 3.7 V mV A mA 2 MOTOROLA ANALOG IC DEVICE DATA AAAA A A A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAA A A A A AAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A AAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AA A A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AA A A A A AAAAA AAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA ELECTRICAL CHARACTERISTICS (continued) (Pin 1 connected to Pin 2, for typical values TJ = 25C, for min/max values TJ is the operating junction temperature range that applies (Note 2), unless otherwise noted.) CURRENT LIMIT AND THERMAL PROTECTION Current Limit Threshold (Note 4, TJ = 25C) MC33369 MC33370 MC33371 MC33372 MC33373A MC33373 MC33374 Propagation Delay, Current Limit Threshold to Power Switch Circuit Output Pin 5 (Leading Edge Blanking plus Current Limit Delay) POWER SWITCH CIRCUIT (Pin 5) On Resistance Pin 5 to Pin 3 MC33369, MC33370 (I5 = 50 mA) TJ = 25C TJ = 125C MC33371 (I5 = 100 mA) TJ = 25C TJ = 125C MC33372 (I5 = 150 mA) TJ = 25C TJ = 125C MC33373A (I5 = 175 mA) TJ = 25C TJ = 125C MC33373 (I5 = 200 mA) TJ = 25C TJ = 125C MC33374 (I5 = 250 mA) TJ = 25C TJ = 125C Breakdown Voltage Pin 5 (I5(off) = 100 A, TA = 25C) Off-State Leakage Current Pin 5 (V5 = 700 V) TJ = 25C TJ = 125C Switching Characteristics (V5 = 50 V, RL set for I5 = 0.7 Ilim) Turn-on Time (90% to 10%) Turn-off Time (10% to 90%) Thermal Protection (Note 1, 3) Shutdown (Junction Temperature Increasing) Hysteresis (Junction Temperature Decreasing) Characteristic MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 R5,3(on) Symbol V(BR)5 I5(off) tPLH Ilim ton toff tsd tH 0.44 0.8 1.3 1.8 2.2 2.4 2.9 - Min 140 - 700 - - - - - - - - - - - - - - - - Typ 157 15 0.5 0.9 1.5 2.0 2.5 2.7 3.3 280 28 100 3.0 5.4 3.8 6.8 4.0 7.2 4.8 8.0 6.8 13 10 15 12 21 - 0.56 1.0 1.7 2.2 2.8 3.0 3.7 - 7.5 14.5 13.5 30 Max 50 200 3.5 6.5 4.5 8.5 5.0 9.5 5.5 9.0 - - - - - Unit V A C ns ns A 3 MC33369 thru MC33374 ELECTRICAL CHARACTERISTICS (continued) (Pin 1 connected to Pin 2, for typical values TJ = 25C, for min/max values TJ is the operating junction temperature range that applies (Note 2), unless otherwise noted.) Characteristic STARTUP CONTROL (Pin 1) Undervoltage Lockout Start-Up Threshold (VCC Increasing) Minimum Operating Voltage After Turn-On Hysteresis Start-Up Circuit Pin 1 Output Current (Pin 5 = 50 V) VCC = 0 V VCC = 8.0 V Auto Restart (CPin 1 = 47 F, Pin 5 = 50 V) Duty Cycle Frequency TOTAL DEVICE (Pin 1) Power Supply Current After UVLO Turn-On Power Switch Circuit Enabled MC33369, MC33370 MC33371 MC33372 MC33373A, MC33373 MC33374 Power Switch Circuit Disabled Symbol Min Typ Max Unit V AAAA A A A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAA A A A A AAAAA AAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA VCC(on) VCC(min) VH Istart 8.2 7.2 0.8 1.2 0.5 - - 8.5 7.5 1.0 2.0 1.4 5.0 1.2 8.8 7.8 1.2 2.5 2.5 - - mA Drst frst % Hz mA ICC1 ICC2 0.5 0.65 0.8 0.95 1.1 0.6 1.2 1.4 1.5 1.7 1.8 1.0 1.7 1.8 1.9 2.1 2.2 1.2 NOTES: 1. Maximum Package power dissipation limits must be observed. 2. Tested junction temperature range for the MC33370 series: Tlow = -40C Thigh = +125C 3.Guaranteed by design only. 4.Adjust di/dt to reach Ilim in 5.0 s. 4 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 f OSC , NORMALIZED OSCILLATOR FREQUENCY (kHz) Figure 1. Oscillator Frequency Change versus Temperature 120 Ifb = 4.0 mA 110 Iin , STATE CONTROL INPUT CURRENT (mA) 3.0 Figure 2. State Control Input Current versus Input Voltage Ifb = 4.0 mA TA = 25C 2.0 Input Zener Clamp 100 1.0 90 0 Input Open Circuit Voltage -1.0 0 2.0 4.0 Input PNP Transistor Clamp 80 -50 -25 0 25 50 75 100 125 150 6.0 8.0 10 TC, CASE TEMPERATURE (C) Vin, STATE CONTROL INPUT VOLTAGE (V) Figure 3. State Control Input Threshold Voltage versus Temperature 4.6 V th , INPUT THRESHOLD VOLTAGE (V) Set Comparator Threshold, Vin Increasing 4.4 4.2 2.3 2.1 1.9 1.7 -50 Toggle Comparator Hysteresis, Vin Increasing Toggle Comparator Threshold, Vin Decreasing -25 0 25 50 75 100 125 150 Vin , INPUT VOLTAGE (V) Ifb = 4.0 mA 9.0 5.7 5.3 3.6 3.5 -50 11 Figure 4. State Control Input Open Circuit and Clamp Voltages versus Temperature Input Zener Clamp Voltage at 10 mA Input PNP Clamp Voltage at 0.5 mA Input Open Circuit Voltage -25 0 25 50 75 100 Ifb = 4.0 mA 125 150 TC, CASE TEMPERATURE (C) TC, CASE TEMPERATURE (C) Figure 5. Power Switch Circuit Output Duty Cycle versus Feedback Input Current 80 IFB , FEEDBACK INPUT CURRENT (mA) Threshold of Duty Cycle Reduction Auto Restart Hysteretic Operation D, OUTPUT DUTY CYCLE (%) 60 Pin 1 Connected to Pin 2 TA = 25C MC33369/ MC33370 100 Figure 6. Feedback Input Current versus Input Voltage Pin 1 Connected to Pin 2 TA = 25C 80 60 Input Resistance 40 20 0 40 MC33374 DVFB DIFB 20 Power Supply Current After UVLO Turn-On 2.0 4.0 6.0 8.0 10 0 0 IFB, FEEDBACK INPUT CURRENT (mA) 0 2.0 4.0 6.0 8.0 10 12 VFB, FEEDBACK INPUT VOLTAGE (V) MOTOROLA ANALOG IC DEVICE DATA 5 MC33369 thru MC33374 V reg(fb), SHUNT REGULATION VOLTAGE (V) 8.9 6.0 Ifb , FEEDBACK CURRENT (mA) VCC , STARTUP and MINIMUM OPERATING VOLTAGE (V) Figure 7. Feedback Input Shunt Regulation Voltage and Current versus Temperature Pin 1 Connected to Pin 2 Feedback Input Current for 35% Power Switch Circuit Output Duty Cycle Figure 8. Undervoltage Lockout Thresholds versus Temperature 8.8 Startup Threshold Voltage, VCC Increasing 8.4 8.8 5.0 8.7 4.0 8.0 8.6 Shunt Regulator Voltage Ifb = 4.0 mA 8.5 -50 -25 0 25 50 75 100 125 3.0 7.6 Minimum Operating Voltage, VCC Decreasing 2.0 150 7.2 -50 -25 0 25 50 75 100 125 150 TC, CASE TEMPERATURE (C) TC, CASE TEMPERATURE (C) Figure 9. Start-Up Circuit Current versus Pin 5 Voltage Istart , START-UP CIRCUIT CURRENT (mA) Current Into Pin 5 2.0 Current Out of Pin 1 1.6 1.2 0.8 0.4 0 VCC = 5.0 V Tcase = 25C 10 100 V5, PIN 5 VOLTAGE (V) 1000 Istart , START-UP CIRCUIT CURRENT (mA) 2.4 2.4 Figure 10. Start-Up Circuit Current versus Power Supply Voltage Current Into Pin 5 2.0 Current Out of Pin 1 1.6 1.2 0.8 0.4 0 0 2.0 4.0 6.0 8.0 10 VCC, POWER SUPPLY VOLTAGE (V) V5 = 400 V Tcase = 25C Ilim , NORMALIZED CURRENT LIMIT THRESHOLD Figure 11. Power Switch Circuit Current Limit Threshold versus Temperature 1.2 IPK, NORMALIZED PEAK CURRENT Vfb Adjusted for an Initial ton of 2.0 ms 2.0 1.8 1.6 1.4 1.2 1.0 -25 0 25 50 75 100 125 150 0 Figure 12. Power Switch Circuit Peak Current versus Current Rate of Change V5(off) = 400 V Tcase = 25C MC33369/ MC33370 MC33371 MC33372 MC33373A/ MC33373/ MC33374 2.0 4.0 6.0 8.0 10 1.1 1.0 0.9 0.8 -50 TC, CASE TEMPERATURE (C) DI/Dt, CURRENT RATE OF CHANGE (A/ms) 6 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 R5,3(on) , NORMALIZED PIN 5 TO PIN 3 ON-RESISTANCE Figure 13. Power Switch Circuit Current versus Pin 5 Voltage 3.0 ton = 1.0 ms Tcase = 25C I 5 , PIN 5 CURRENT (A) 2.0 MC33372 1.0 MC33371 MC33369/ MC33370 0 0 2.0 4.0 6.0 8.0 10 V5, PIN 5 VOLTAGE (V) MC33374 MC33373 MC33373A Figure 14. Normalized Power Switch Circuit On-Resistance Pin 5 to Pin 3 versus Temperature 2.0 1.8 1.6 1.4 1.2 1.0 0.8 0.6 -50 -25 0 25 50 75 100 125 150 ton = 1.0 ms I5 = 250 mA TC, CASE TEMPERATURE (C) I 5(off) , OFF-STATE PIN 5 CURRENT ( m A) 104 Figure 15. Power Switch Circuit Off-State Current versus Voltage 500 COSS, CAPACITANCE (pF) VCC Power Up Sequence: 1) 0 to 8.6 V, Start-Up Circuit Turn Off 2) 8.6 V to 7.0 V, Power Switch Circuit Turn Off 3) 7.0 V to 8.6 V, Measure I5 Current Power Switch Circuit Breakdown Voltage Tcase = 150C Tcase = -50C Start-Up Circuit Bias Current 0 200 400 600 Tcase = 25C 0 800 1000 400 300 200 Figure 16. Power Switch Circuit Capacitance versus Pin 5 Voltage VCC Power Up Sequence: 1) 0 to 8.6 V, Start-Up Circuit Turn Off 2) 8.6 V to 7.0 V, Power Switch Circuit Turn Off 3) 7.0 V to 8.6 V, Measure Capacitance MC33373A MC33372 MC33371 100 Tcase = 25C COSS measured at 1.0 MHz with 50 mVpp MC33369/ MC33370 MC33374 MC33373 103 102 101 1.0 10 100 1000 V5, PIN 5 VOLTAGE (V) V5, PIN 5 VOLTAGE (V) Figure 17. Pin Function Description A A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AA AAAAAAAAAAAAAAAAAAAAAAAA A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAA 1 VCC This is the positive supply voltage input. During startup, power is supplied to this input from Pin 5. When VCC reaches the UVLO upper threshold, the Start-Up circuit turns off and power is supplied from an auxiliary transformer winding. This is the Shunt Regulator/Amplifier input and is used to duty cycle control the Power Switch circuit. It has an 8.6 V threshold and normally connects to the converter output, or to a voltage that represents the converter output. This pin is the control circuit and Power Switch circuit ground. It is part of the integrated circuit lead frame and is electrically common to the metal heatsink tab. This is a multifunction input that is designed to interface with a small number of external components to implement various methods of converter on/off control. 2 Feedback Input 3 4 5 Ground State Control Input Power Switch Pin This pin is designed to directly drive the converter transformer primary, and internally connects to the Power Switch circuit and Start-Up circuit. Pin Function Description MOTOROLA ANALOG IC DEVICE DATA 7 MC33369 thru MC33374 Figure 18. Representative Block Diagram AC Line Input + Auxiliary Power Supply + Feedback VCC 1 Feedback Input 2 15 + + Auto Restart Timing/ Loop Compensation/ Power Supply Bypass 8.6 V Ifb Oscillator Duty Cycle PWM Latch Clock Ramp 7.0 kHz Filter PWM Comparator S Q R Minimum On-Time Delay Leading Edge Blanking Shunt Regulator/ Amplifier Thermal Shutdown Power-Up Reset External Shutdown 10 V 10 V Undervoltage Lockout 8.5 V/ 7.5 V + Power Switch Pin 5 Start-Up Circuit State Control Input Internal Bias State Control 10 V Ck Shutdown Latch R Q S Driver R On/Off Toggle Power Switch Circuit 4 - Converter DC Output Snubber + + Divide by 8 Q Rfb Current Limit Comparator + Rpk Ground 3 Figure 19. Pulse Width Modulation Timing Diagram Feedback Input (Rfb Voltage) Oscillator Ramp Oscillator Duty Cycle Oscillator Clock PWM Comparator Output PWM Latch Q Output Power Switch Circuit Gate Drive Leading Edge Blanking Input (Power Switch Circuit Current) Minimum On-Time Current Limit Propagation Delay Current Limit Threshold Normal PWM Operating Range Output Overload 8 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 OPERATING DESCRIPTION Introduction The MC33369 thru MC33374 represent a new higher level of integration by providing on a single monolithic chip all of the active power, control, logic, and protection circuitry required to implement a high voltage flyback, forward, boost, or buck converter. This device series is designed for direct operation from a rectified 240 VAC line source and requires minimal external components for a complete cost sensitive converter solution. Potential markets include office automation, industrial, residential, personal computer, and consumer. A description of each of the functional blocks is given below, and the representative block diagram is shown in Figure 18. Oscillator The Oscillator block consists of two comparators that alternately gate on and off a trimmed current source and current sink which are used to respectively charge and discharge an on-chip timing capacitor between two voltage levels. This configuration generates a precise linear sawtooth ramp signal that is used to pulse width modulate the MOSFET of the Power Switch circuit. During the charge of the timing capacitor, the Oscillator duty cycle output holds one input of the Driver low. This action keeps the MOSFET of the Power Switch circuit off, thus limiting the maximum duty cycle. The Oscillator frequency is internally programmed for 100 kHz operation with a controlled charge to discharge current ratio that yields a maximum PWM duty cycle of 74%. The Oscillator temperature characteristics are shown in Figure 1. PWM Comparator and Latch The pulse width modulator (PWM) consists of a comparator with the Oscillator ramp output applied to the inverting input, while the Amplifier output is applied into the noninverting input. The Oscillator clock output applies a set pulse to the PWM Latch when the timing capacitor reaches its peak voltage, initiating Power Switch circuit conduction. As the timing capacitor discharges, the ramp voltage decreases to a level that is less than the Amplifier output, causing the PWM Comparator to reset the latch and terminate Power Switch circuit conduction for the duration of the ramp-down period. This method of having the Oscillator set and the PWM Comparator reset the Latch prevents the possibility of multiple output pulses during a given Oscillator clock cycle. This circuit configuration is commonly referred to as double pulse suppression logic. A timing diagram is shown in Figure 19 that illustrates the behavior of the pulse width modulator. Shunt Regulator/Amplifier Feedback Input, Pin 2, connects to the internal Shunt Regulator/Amplifier. This input is used as a means to close the feedback loop for converter output regulation. The internal circuitry consists of an Amplifier with a precise threshold that drives a MOSFET in a manner that forms an active Shunt Regulator. The initial current that flows into Pin 1 is used to bias the internal circuitry. Any additional current is in excess flows into Pin 2, and is shunted through resistor Rfb to ground. The voltage developed across Rfb is used to adjust the PWM Comparator threshold, which in turn controls the PWM duty cycle. The duty cycle is inversely proportional to the input current level that in excess of about 2 mA, and is reduced at a rate of about -14% per mA, refer to Figure 5. A 7.0 kHz low pass filter is placed between Rfb and the PWM input. This filter attenuates any switching noise that may be present and reduces the possibility of output pulse width jitter. MOTOROLA ANALOG IC DEVICE DATA The Amplifier gain is set by the dynamic impedance of the feedback input and is nominally centered at 18 W. The dynamic impedance of this pin combined with the external resistive and capacitive components determines the control loop characteristics of the converter. The feedback input has a temperature compensated threshold of 8.6 V and is used as a voltage reference in non-isolated output applications. The input dynamic resistance is shown in Figure 6. External Shutdown and Latch A latching shutdown feature has been incorporated into this device series to eliminate the possibility of converter runaway output voltage during a sudden load removal. The External Shutdown block sets the Shutdown Latch when the feedback input current exceeds 60 mA. When set, the Latch holds the MOSFET of the Power Switch circuit off, and the Start-Up circuit hystereticly regulates the VCC Pin 1 voltage between 8.5 V to 7.5 V. In order to resume the switching operation, the Shutdown Latch must be reset by the Power-Up Reset block. This can be accomplished directly by momentarily pulling the VCC Pin 1 below the 3.7 V Power-Up Reset threshold, or indirectly by removing, waiting, and then restoring power to the converter input. The Power-Up Reset block automatically resets the Shutdown Latch each time power is applied to the device. Current Limit Comparator and Power Switch Circuit This device series uses cycle-by-cycle current limiting as a means of protecting the output switch circuit from overstress. Each on-cycle is treated as a separate situation. Current limiting is implemented by monitoring the output switch circuit current buildup during conduction, and upon sensing an overcurrent condition, immediately turning off the switch circuit for the duration of the oscillator ramp-down period. The Power Switch circuit is constructed as a SENSEFET circuit with a high voltage JFET in series with a low voltage MOSFET. The drain of the high voltage JFET is connected to Pin 5. The gate of the JFET is grounded. The source of the JFET is connected to the drain of the low voltage MOSFET. The MOSFET has two sources of different size with a known ratio of about 1:100. One source of the MOSFET is connected to Pin 3 and provides the main current conduction path between Pin 5 and Pin 3. The second source of the MOSFET is used for current sensing by conducting a small percentage of the current between Pin 5 and Pin 3 through a ground referenced sense resistor, RPK. The voltage across sense resistor RPK represents the current from Pin 5 to Pin 3 divided by the known ratio of the MOSFET sources. The SENSEFET circuit allows a virtually lossless method of monitoring the current from Pin 5 to Pin 3. The current limit comparator detects if the voltage across Rpk exceeds the reference level that is present at the noninverting input. If exceeded, the comparator quickly resets the PWM Latch, thus protecting the Power Switch circuit. Figure 11 shows that this detection method yields a relatively constant current limit threshold over temperature. The high voltage Power Switch circuit is integrated with the control logic circuitry and is designed to directly drive the converter transformer. The Power Switch circuit is capable of switching 700 V with an associated current from Pin 5 to Pin 3 that ranges from 0.9 A to 3.3 A. Proper voltage snubbing on Pin 5 during converter startup and overload is mandatory for reliable device operation. A Leading Edge Blanking circuit was placed in the current sensing signal path to prevent a premature reset of the PWM Latch. A potential premature reset signal is generated each time 9 MC33369 thru MC33374 the Power Switch circuit is driven into conduction and appears as a narrow voltage spike across the current sense resistor Rpk. The spike is due to the low voltage MOSFET gate to source capacitance, transformer interwinding capacitance, and output rectifier recovery time. The Leading Edge Blanking circuit has a dynamic behavior that masks the current signal until the Power Switch circuit turn-on transition is completed. The current limit propagation delay time is typically 280 ns. This time is measured from when an overcurrent appears in the Power Switch circuit, to the beginning of turn-off. Care must be taken during transformer saturation so that the maximum device current limit rating is not exceeded. Figure 20. Startup and Normal Operation Timing Diagram 8.5 V 7.5 V Shunt Regulation Threshold Feedback Input Voltage (Pin 2) 0V Flyback Voltage Power Switch Voltage (Pin 5, Pin 3) Switching Disabled Startup Switching Normal Operation Rectified Line Voltage 0V Figure 21. Auto Restart Operation Timing Diagram 1 Hysteretic Regulation Start-Up Circuit Feedback Input Voltage (Pin 2) On Istart Off ICC1 On Off On Off On Off Istart ICC2 Istart ICC2 Istart ICC1 35% 65% 2 7 8 1 2 7 8 1 8.5 V 7.5 V Start-Up Circuit Duty Cycle During Auto Restart, External Shutdown, Thermal Shutdown, and State Control Off Mode 0V Flyback Voltage Rectified Line Voltage Eight Cycles Power Switch Voltage (Pin 5) Switching Disabled Startup Switching Switching Disabled Power Switch Circuit Duty Cycle During Auto Restart 5% 95% 0V Switching Switching Disabled Switching Auto Restart Operation with Overloaded or Shorted Output 10 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 Start-Up Circuit Contained within the MC33369 thru MC33374 is a Start-Up circuit that is governed by the State Control block. The Start-Up circuit includes a high voltage JFET and a low voltage MOSFET. The drain of the high voltage JFET is connected to Pin 5. The gate of the JFET is grounded. The source of the high voltage JFET is connected to the drain of the low voltage MOSFET. The JFET pinches off and clamps the voltage on the drain of the MOSFET to a low voltage between 18-24 volts. A resistance of 550K ohms is connected between the drain and gate of the low voltage MOSFET. The low voltage on the drain and gate of the MOSFET simplifies construction of the Start-Up circuit. This circuitry yields an increase in converter efficiency by the elimination of an external startup resistor and its associated power dissipation that is common in most of the off-line converters that utilize a UC3842 type of controller. Rectified AC line voltage is applied to the Start-Up circuit from Pin 5. This enables the Start-Up circuit to provide charge current to the VCC bypass capacitor that connects from Pin 1 to ground. When VCC reaches the UVLO upper threshold of 8.5 V, the Start-Up circuit is turned off to complete the startup phase. The IC then commences normal operation. As the converter output approaches regulation, the auxiliary transformer winding begins to provide operating bias. All of the required device power is now efficiently converted down directly from the rectified AC line. The Start-Up circuit will provide an initial charging current of 2.0 mA when powered from 400 V. This current will decrease as the VCC pin voltage rises or if the device is powered from a lower input voltage, refer to Figures 9 and 10. The Start-Up circuit is rated at a maximum of 700 V with the VCC pin shorted to ground. Undervoltage Lockout An Undervoltage Lockout comparator is included to guarantee that the integrated circuit has sufficient voltage to be fully functional before the output stage is enabled. The UVLO comparator monitors the feedback input voltage at Pin 2 and when it exceeds the startup threshold of 8.5 V, the Start-Up circuit turns off, the Internal Bias block is switched on, and the Power Switch circuit is enabled. To prevent erratic switching as the threshold is crossed, 1.0 V of hysteresis is provided. This level of hysteresis ensures that there is sufficient energy stored in the VCC bypass capacitor to power the bias circuitry until auxiliary power supply takes over. If the converter output is nominally loaded, regulation will be established and the opto-isolator will provide sufficient current into the feedback input to keep the VCC bypass capacitor charged. Figure 20 shows the timing waveforms during startup and normal operation. If the converter output is overloaded or shorted, the device will enter into the auto restart mode. This happens when the opto-isolator is not able to provide sufficient current into the feedback input to keep the VCC bypass capacitor charged. When the capacitor voltage falls below the minimum operating threshold of 7.5 V, the UVLO comparator switches the Internal Bias block off, and disables the Power Switch circuit. The Start-Up circuit is turned on and the VCC bypass capacitor begins charging. When the UVLO startup threshold is reached, the Start-Up circuit again turns off, the Internal Bias block is switched on, and the Divide by 8 counter is clocked. Since the Power Switch circuit is now disabled by the Divide by 8 counter, the opto-isolator will not provide current to the VCC bypass capacitor, the capacitor will discharge. The UVLO comparator and Start-Up circuit will regulate the capacitor voltage in a hysteretic mode, varying between 7.5 V to 8.5 V, with an effective ramp-up duty cycle of approximately 35%. The Divide by 8 counter will enable the Power Switch circuit to burst at the 100 kHz Oscillator frequency on every eighth ramp-down cycle. The device will remain in the auto restart mode until the output overload or short is removed and the threshold of regulation can again be reached. The purpose of the Divide by 8 counter is to reduce the Power Switch circuit and output rectifier power dissipation when the converter is subjected to an output overload or short. The counter effectively limits the average switching duty cycle to approximately 5%. Figure 21 shows the timing waveforms when in auto restart mode. Thermal Shutdown and Package The internal Thermal Shutdown block protects the device in the event that the maximum junction temperature is exceeded. When activated, typically at 157C, one input of the Driver is held low to disable the Power Switch circuit. When disabled, the UVLO comparator and Start-Up circuit regulate the VCC pin voltage in the hysteretic mode. Thermal shutdown activation is non-latching and the Power Switch circuit is allowed to resume operation when the junction temperature falls below 140C. The thermal shutdown feature is provided to prevent catastrophic device failures from accidental overheating. It is not intended to be used as a substitute for proper heatsinking. The die in the 8-pin dual-in-line package is mounted on a special heat tab copper alloy lead frame. The tab consists of pins 3, 6, 7, 8 is specifically designed to improve the thermal conduction from the die to the printed circuit board. This permits the use of standard layout and mounting practices while having the ability to halve the junction to air thermal resistance. The die in the 5 pin TO-220 style package is mounted directly on a copper alloy heat tab. This metal tab is exposed on the back side of the package for heatsink attachment and is electrically common to the device ground, Pin 3. A wide variety of TO-220 style heatsinks are commercially available for enhancing the thermal performance and converter output power capability. State Control The State Control block is designed to interface with a small number of external components to implement various methods of converter on/off control. By utilizing the distinctive features of the State Control Input, this device series can be programmed to enter into either the standby* or operating mode in response to an appropriate input stimulus. This stimulus can come from a user interface pushbutton switch, an optically coupled microcontroller output signal, a combination of both, or other circuit configurations. The State Control Logic can be disabled and made to appear transparent when converter on/off control is not required. Figures 22 and 23 respectively show the State Control operating table, and the Control Block along with seven input examples. The State Control block consists of a resistor bias network, Toggle and Set Comparators for threshold detection, an Input Clamp to provide drive for an opto light emitting diode, control logic elements for storing the operating state, and a Reset MOSFET for discharging an MOTOROLA ANALOG IC DEVICE DATA 11 MC33369 thru MC33374 external capacitor. The State Control Input is internally biased at 3.55 V when the VCC input is regulated at 8.6 V. This internal bias can be overridden and driven either low or high by an external signal in order to trip one of the comparators. The Toggle and Set Comparator thresholds are respectively at 1.8 V and 4.4 V. The comparator outputs are processed and stored by the State Control Logic block which in turn controls the Start-Up circuit, Internal Bias block, and the Divide by 8 reset. Circuit A shows an input configuration for manual toggle operation. A toggle request is made each time the pushbutton switch is pressed and released. When the Toggle Comparator detects a request, its output clocks the State Control Logic, resulting in a converter mode change. Successive toggle requests causes the converter to alternate between the standby* and operating modes. When in standby* mode, the UVLO comparator and Start-Up circuit regulate the VCC pin voltage in the hysteretic mode, and there is not any voltage present at the converter output. Circuit B configures the input to interface with a microcontroller for graceful shutdown operation. Graceful shutdown is an advanced form of power management where the microcontroller has the overriding responsibility for determining if and when the converter enters into the standby* mode. This is usually programmed to occur after the microcontroller completes a set of housekeeping routines. A toggle request is made each time the pushbutton switch is pressed and released. When the Set Comparator detects a request, its output sets the State Control Logic, causing the converter to enter the operating mode. If the converter was initially operating, no mode change takes place. Note that each toggle request is conveyed to the microcontroller via Opto A. A current path for biasing the light emitting diode is provided by the series resistor and the internal 5.5 V Input Clamp. The microcontroller receives and processes the toggle request and upon completion of a maintenance routine, it sends a toggle confirm signal back to the State Control input via Opto B. This signal is detected by the Toggle Comparator and the converter enters into the standby* mode. With this circuit configuration, the user only has control of the standby* to operating mode transition. The user can request the operating to standby* mode transition, but the microcontroller has total control on executing the request. Circuit C configures the input for brownout protection. The cathode of the zener diode connects to the rectified and filtered AC line voltage that appears at the positive terminal of bulk capacitor C1. With appropriate zener diode and resistor values, the State Control Input voltage can be set to fall below 1.8 V during a brownout condition. This results in a toggle request that causes the converter to incisively change from operating to standby* mode without any converter output voltage bounce. When the AC line voltage returns back to nominal, the voltage at the State Control Input rises, causing the Set Comparator to change the converter mode from standby* to operating. Note that when the converter is in standby*, the Set Comparator threshold will be lower than specified, and is approximately 3.84 V. This is because VCC is regulated in the hysteretic mode between 7.5 V to 8.5 V. Circuit D shows a method of accomplishing digital on/off control of the converter. Pull-up resistor R serves to bias the Set Comparator for turn-on, while the NPN transistor biases the Toggle Comparator for turn-off. An economical optocoupler can be used if galvanic isolation of the signal source is required. Capacitor Cst shown in each of the examples provides an important programming function. A small value capacitor (0.05 F) serves to filter noise that may be coupled into the state control pin, thereby preventing false triggering of the comparators. A relatively large value capacitor (2.0 F) will delay the initial rise of the state control voltage during startup. This action results in the converter powering up in standby* rather than the operating mode. Circuit E configures the State Control Input to provide a power-up time delay of the converter. Upon the initial application of AC power, the large value of capacitor Cst causes the Toggle Comparator to place the converter in standby*. When pull-up resistor R charges Cst to the Set Comparator threshold, the converter changes to the operating mode. A graph of power-up time delay versus resistance for three values of Cst is shown. The circuits shown in the example in Circuit F on page 13 exemplifies two possible methods of disabling the State Control block on/off capability, thus rendering it transparent. This feature is useful in applications where converter on/off control is not desired. When nominal AC line voltage is applied to the converter input, the resistor circuit will cause the Set Comparator to place the converter in the operating mode. The resistor value is not critical, but it should be at least 5.0 k to insure proper device start-up. The converter will also assume the operating mode if the State Control Input is left open or unconnected. Due to the relatively high input impedance, this input may be susceptible to noise pickup. A small bypass capacitor in the range of 1.0 nF to 50 nF is recommended for Cst. The converter will assume the operation mode with either of these circuits. Applications The TO220 devices have a single Ground, Pin 3, that serves as both a sense point for the Shunt Regulator/Amplifier and the high current return path for the power switch circuit. Do not attempt to construct a converter circuit on a wire-wrap or plug-in prototype board. In order to ensure proper device operation and stability, it is important to minimize the lead length and the associated inductance of the ground pin. This pin must connect as directly as possible to the printed circuit ground plane and should not be bent or offset by the board layout. The Power Switch Pin 5 can be offset using a TV suffix product if additional layout creepage distance is required. Due to the potentially high rate of change in switch circuit current, components R3 and C5 must be connected to IC1 through separate and short copper traces. This will significantly reduce the level of switching noise that can be imposed upon the feedback control signal. Figures 24 through 27 show a universal input 52 watt 90 watt converter with the associated test data. The converters were constructed and tested using the printed circuit board layout shown in Figure 28. The board consists of a fiber glass epoxy material (FR4) with a single side of two ounce per square foot copper foil. It is designed as a general purpose single output laboratory test vehicle and therefore does not contain an input electromagnetic interference (EMI) filter. The board layout is capable of encompassing the wide range of output power available from the TO220TV package devices by providing a means to accept several component 12 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 sizes and styles. Note that there are multiple positions for output filter capacitors C8 and C11, allowing up to four capacitors in parallel. The various positions for transformer T1 will accomodate four core/bobbin sizes, consisting of E19/8/5 (E187), E22, E25/10/6 (E250), and E28. Unused pins must be removed from the bobbin. A choice of four TO220 style heatsinks can be used for integrated circuit IC1 and output rectfier D7. They are available from several manufacturers including Aavid Engineering. The table shown below lists the Aavid part numbers along with the associated thermal characteristics. The extruded heatsink must be drilled and tapped to allow attachment of the device and the printed circuit board. Heatsink junction temperature and current limit threshold of the device selected. The table below provides a general guide for device selection assuming the following conditions: Discontinuous mode flyback operation Wide range input operation from 92 VAC to 276 VAC Bulk capacitor C1 ripple voltage 25 Vpp at 92 VAC input Converter efficiency of 75% Ambient temperature of 25C Adequate heatsinking for a junction temperature 150C Device MC33369P MC33370P MC33371P MC33372P Converter Output Power (W) 12 20 30 35 40 12 25 45 60 75 90 AAAAAA A A AAAAAAAAAAAAAAAAA A A AAAAAA A A AAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAA AAAAAA A AAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAA AAAAAAAAAAAA AAAAAAA 592502B03400 593002B03400 593202B03500 590302B03600 604953B02500 Stamped Stamped Stamped Stamped 24 at 2.0 W 14 at 4.0 W 10.4 at 5.0 W 9.2 at 5.0 W 6.0 at 15 W Extruded Aavid Part A id P Number Style Thermal Resistance (C/W) The maximum output power that can be obtained from a given converter design is limited by the maximum operating MOTOROLA ANALOG IC DEVICE DATA AAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAA A AAAAAAAAAAAAAAAA AAAAAAAA AAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA AAAAAAAA AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA AAAAAAAA AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA AAAAAAAA AAAAAAAAAAAAAAAA A MC33373AP MC33369T/TV MC33370T/TV MC33371T/TV MC33372T/TV MC33373T/TV MC33374T/TV 13 MC33369 thru MC33374 Figure 22. State Control Operating Table (Circuits A through D of Figure 23) A A A AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A A AA AA AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A A A A AA AA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAA A A A AAAAAAAAAAAAAAA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAA A AA AA AA AA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAA A A A A A A AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAA A AA AA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAA A AA AA AA AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAA A A A A A AA A AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AA AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAA A AA AA AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA AAAAAAAAAAAAAAAA A A A A A AA AA A AA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAA A AA AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A AA AA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A AA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AA AA AAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAA AAAAAAAAAAAAAAAAAAA A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAA A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A Initial State Subsequent State AC Line Voltage Converter Mode Input (Pin 4) Capacitor Stimuli Converter Mode Description TOGGLE OPERATION (Circuit A) Nominal Nominal Standby Don't Care Don't Care Pulsed Low 1.8 V Pulsed Low 1.8 V Operating Standby The converter changes from standby to operating mode by the Toggle Comparator. Operating The converter changes from operating to standby* mode by the Toggle Comparator. MICROCONTROLLER GRACEFUL SHUTDOWN (Circuit B) Nominal Nominal Standby Don't Care Don't Care Pulsed High 4.4 V Pulsed High 4.4 V Pulsed Low 1.8 V Operating Operating Converter mode toggle requested. The Set Comparator changes the converter mode from standby to operating. Operating Converter mode toggle requested. No mode change takes place since the converter was initially operating. The change request is communicated to the MCU via Opto A. Converter mode toggle is confirmed by the MCU via Opto B. The converter mode changes from operating to standby. Nominal Operating Don't Care Standby BROWNOUT PROTECTION (Circuit C) Nominal to Brownout Operating Don't Care Biased Low 1.8 V Standby The AC line voltage level changes from nominal to brownout and zener diode breakdown ceases. The lower divider resistor biases the Toggle Comparator input low, changing the converter mode from operating to standby. The AC line voltage level changes from brownout to nominal and zener diode commences breakdown. This biases the Set Comparator input high, changing the converter mode from standby to operating. Brownout to Nominal Standby Cst 0.05 F Biased High 3.85 V Operating DIGITAL ON/OFF CONTROL (Circuit D) Nominal Nominal Standby Don't Care Don't Care Biased High 4.4 V Biased Low 1.8 V Operating Standby The transistor is off and the collector resistor biases the Set Comparator input high, placing the converter in the operating mode. The transistor is on and the collector biases the Toggle Comparator input low, placing the converter in the standby mode. Operating DELAYED POWER-UP (Circuit E) Zero to Nominal Off Cst 2.0 F Pulsed Low by Cst 1.8 V Set High 4.4 V Off Delay Operating Discharged capacitor Cst causes the Toggle Comparator to change the control logic state. The converter is placed in the standby mode with the power switch circuit disabled. When Cst charges above 4.4 V, the Set Comparator changes the converter mode from standby to operating. POWER-UP (Circuits A, and B) Zero to Nominal Zero to Nominal Off Cst 0.05 F None Operating Application of AC line power causes converter operation. The State Control Input is presently configured to be transparent and the control logic has no effect during power-up. Discharged capacitor Cst causes the Toggle Comparator to change the control logic state. The converter is placed in the standby mode with the power switch circuit disabled. Off Cst 2.0 F Pulsed Low by Cst 1.8 V Standby NOTE: When the converter is in the standby mode, there is not any voltage present at the output. 14 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 Figure 23. State Control Block with Input Control Examples 10 W to 10 k R Cst Manual Toggle Operation (Circuit A) Resistor R is required for proper toggle functionality when operating the device at an elevated temperature with long leads to the pushbutton switch. Toggle Request Primary Common Vaux MCU Graceful Shutdown (Circuit B) Toggle Request Toggle Confirm + Printer Port Microcontroller Control Outputs Isolation Boundary - Secondary Common (on to off) AC blk Internal State Control Block Functional Diagram MC33369 thru MC33374 VCC 1 8.6 V 10 V 4 165 k 3.55 V 4.4 V Set Comparator Input Clamp 5.5 V 1.8 V 1.8 V/ 2.0 V Reset Toggle Comparator State Control Logic 10 V State Control Input Power Switch Pin 5 Start-Up Circuit Cst R Primary Common Vbulk VZ R2 Brownout Protection (Circuit C) Choose VAC(on to off) and VAC(off to on) thresholds. Determine converter output power PO, efficiency h, and input bulk capacitance Cblk. blk(max) 116 k To Internal Bias and Divide by 8 Reset [ VAC(off to on) 2 * 1.4 V + 1.88 V * 0.88 Vblk(max) Z blk(min) R1 Cst V *V V *V R2 + blk(max) Z or blk(min) Z 3.84 1.8 R1 Primary Common P O V [ VAC(on to off) 2 * VAC blk(min) 2f C V Vaux R 5.0 k to 100 k h * 1.4 Digital On/Off Control (Circuit D) 1 = Converter Off 0 = Converter On Digital on/off control of the converter is accomplished with a small signal NPN transistor. An optocoupler can be used if galvanic isolation is required. From VCC Voltage Detector Outputs Cst Primary Common VCC R 100 k to 300 k 10 mF to 100 mF t dly, TIME DELAY (S) Power-Up Time Delay (Circuit E) A programmed power-up time delay can be implemented with the addition of a simple RC circuit. 12 Power-Up Time Delay versus Resistance 100 mF Cst = 50 mF 10 mF 8.0 4.0 0 100 Cst 150 200 Primary Common VCC R 5.0 k to 100 k 1.0 nF to 50 nF R, RESISTANCE (kW) State Control Disabled (Circuit F) The State Control block on/off capability can be disabled and made to appear transparent by either connecting a pull-up resistor from the input to VCC or a small value capacitor from the input to primary common. This input should not be left unconnected since it has a relatively high impedance and may be susceptible to noise pick-up. Cst Primary Common MOTOROLA ANALOG IC DEVICE DATA 15 MC33369 thru MC33374 Figure 24. Universal Input 52 W Off-Line Converter D7 MBR20100CT L1 5.0 mH + 1N5406 D1 92 to 276 VAC Input D3 D2 D4 + C1 100 C2 50 pF R2 3.9 k Z1 1.5KE200A D5 MUR160 D6 + 1/2 IC2 MOC8103 C6 10 MUR 120 C14 1.0 nF T1 + C8 C11 470 470 + 1/2 IC2 MOC 8103 IC3 TL431B C7 0.1 R4 270 R6 75 k + C12 150 15 V/3.5 A DC Output F1 3.0 A R5 15 k C13 1.0 - IC1 MC 33374 R3 3.6 + C5 50 R7 100 C4 0.01 PB1 On/Off Toggle Figure 25. Converter Test Data Test Line Regulation Conditions Vin = 92 Vac to 276 Vac, IO = 3.5 A Vin = 115 Vac, IO = 0.35 A to 3.5 A Vin = 230 Vac, IO = 0.35 A to 3.5 A Vin = 115 Vac, IO = 3.5 A Results A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAA AAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAA AAAAAAAAA Load Regulation Output Ripple Efficiency Vin = 92 Vac to 276 Vac, IO = 3.5 A Vin = 230 Vac, IO = 3.5 A Total = 170 mVp-p 84.4% 86.2% AC Input Power Vin = 115 Vac, Converter Toggle Off 0.06 W 0.19 W Vin = 230 Vac, Converter Toggle Off This data was taken with the components listed below mounted on the printed circuit board shown if Figure 28. C8, C11 = Sanyo Os-Con #16SA470M, 470 F/16V. C12 = IC1, D7 = L1 = T1 = Sanyo Os-Con #10SA150M, 150 F/16V. MC33374, MBR20100 mounted on Aavid #590302B03600 heatsink. Coilcraft S5088-A, 5.0 H, 0.011 W. Coilcraft W7422-A Primary: 49 turns of # 24 AWG, Pin 6 = start, Pin 5 = finish. Two layers 0.002" Mylar tape. Secondary: 9 turns of # 21 AWG, 2 strands bifilar wound, Pins 1 and 2 = start, Pins 9 and 10 = finish. Auxiliary: 7 turns of #24 AWG wound in center of bobbin, Pin 7 = start, Pin 4 = finish. Two layers 0.002" Mylar tape. Gap: 0.017" total for a primary inductance (LP) of 345 H, with a primary to secondary leakage inductance of 14 H. Core: Ferrite International E24/25 (E25/10/6) TSF-7070 material. Bobbin: Philips E24-25PCB1-10, Pins 3 and 8 removed. D = 2.0 mV D = 9.0 mV D = 13 mV 16 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 Figure 26. Universal Input 90 W Off-Line Converter D7 MBR20100CT L1 3.3 mH + 1N5406 D1 92 to 276 VAC Input D3 D2 D4 + C1 330 C2 50 pF R2 3.9 k Z1 1.5KE200A D5 MUR160 D6 + 1/2 IC2 MOC8103 C6 10 MUR 120 C14 1.0 nF IC1 MC 33374 T1 + C8 C11 1000 1000 + 1/2 IC2 MOC 8103 IC3 TL431B C7 0.1 R4 270 R6 75 k + C12 150 15 V/6.0 A DC Output F1 5.0 A R5 15 k C13 1.0 - R3 3.6 + C5 50 R7 100 C4 0.01 PB1 On/Off Toggle Figure 27. Converter Test Data Test Line Regulation Conditions Vin = 92 Vac to 276 Vac, IO = 6.0 A Vin = 115 Vac, IO = 0.6 A to 6.0 A Vin = 230 Vac, IO = 0.6 A to 6.0 A Vin = 115 Vac, IO = 6.0 A Results AAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAA A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAA AAAAAAAAA Load Regulation Output Ripple Efficiency Vin = 92 Vac to 276 Vac, IO = 6.0 A Vin = 230 Vac, IO = 6.0 A Total = 105 mVp-p 83.2% 85.4% AC Input Power Vin = 115 Vac, Converter Toggle Off 0.07 W 0.17 W Vin = 230 Vac, Converter Toggle Off This data was taken with the components listed below mounted on the printed circuit board shown if Figure 28. C8, C11 = Sanyo Os-Con #16SA1000M, 1000 F/16V. C12 = IC1 = Z1 = D7 = L1 = T1 = Sanyo Os-Con #10SA150M, 100 F/16V. MC33374 mounted on Aavid #604953B02500 extruded heatsink. The heatsink must be drilled and tapped to allow device & PCB attachment. 1.5KE200A with cathode lead soldered in the center of a 5/8" x 3/4" x 0.025" thick U-shaped copper heatsink. MBR20100 mounted on Aavid #590302B03600 heatsink. Coilcraft PCV-0-332-10, 3.3 H, 0.005 W. Coilcraft W7518-A Primary: 34 turns of # 24 AWG, Pin 9 = start, Pin 6 = finish. Two layers 0.002" Mylar tape. Secondary: 5 turns of # 20 AWG, 2 strands bifilar wound, Pins 4 and 5 = start, Pins 1 and 2 = finish. Two layers 0.002" Mylar tape. Auxiliary: 4 turns of #24 AWG wound in center of bobbin, Pin 10 = start, Pin 7 = finish. Two layers 0.002" Mylar tape. Gap: 0.022" total for a primary inductance (LP) of 290 H, with a primary to secondary leakage inductance of 7.2 H. Core: TDK PC40 EI28Z, PC40 material. Bobbin: TDK BE-28-1110CPL, Pins 3 and 8 removed. D = 24 mV D = 26 mV D = 10 mV MOTOROLA ANALOG IC DEVICE DATA 17 MC33369 thru MC33374 Figure 28. Printed Circuit Board and Component Layout (Circuit of Figures of 23 and 25) C1 R1 Z1 C2 C3 C14 T1 1 E19/8/5 + - 1 E 22 D5 R7 R2 Toggle On/Off PB1 + C4 D6 D1 F1 D2 D3 D4 AC Line Input 2.50 MC33369 thru 74 18 C C E CCC CCEE C EE ECC CCEE CEEEEEEE C ECC CCEE E EE E EE E EE E EE E EE Caution! High Voltages E 28 1 + R3 IC1 1 C7 R4 - (Top View) 4.00 (Bottom View) MOTOROLA ANALOG IC DEVICE DATA DC Output + C5 C6 + IC2 EE E EE E EE E EE E EE E EE E EE E EEEEEEEEE CCC CCE C ECCC CCC E EEEEEEEEE D7 C8 C9 - + - + C10 - + C11 - + L1 C12 R5 R6 - + C13 IC3 E25/10/6 1 MC33369 thru MC33374 Figure 29. Snubber and Damper Circuits RCD Snubber RC Damper C2 V5 , PIN 5 VOLTAGE (V) + R1 C3 D5 MUR160 + IC1 R2 - + + Pin 5 Turn-Off Voltage 400 300 200 100 0 0 2.0 4.0 6.0 8.0 t, TURN-OFF Time (ms) 10 Substrate forward biased Insufficient Snubbing Pin 5 Turn-Off Voltage V5 , PIN 5 VOLTAGE (V) 400 300 200 100 0 0 2.0 4.0 6.0 8.0 t, TURN-OFF Time (ms) 10 Sufficient Snubbing Converter Figure Output Power T1 Primary Leakage Inductance 14 H 7.2 H Component Values Snubber R1 C3 20 k 2.0 W 10 k 3.0 W 0.1 F 400 V 0.1 F 400 V Damper R2 R2 6.2 k 1.0 W 6.2 k 1.0 W 47 pF 500 V 47 pF 500 V 24 50 W 26 90 W Figures 24 and 26 use zener diode Z1 to limit the voltage on Pin 5 and a damper circuit consisting of resistor R2 and capacitor C2. The zener can be replaced with the snubber circuit shown above consisting of resistor R1 and capacitor C3. The component values selected must insure that the turn-off voltage on Pin 5 never exceeds 700 V under all line voltage and load current conditions when using a transformer with the highest anticipated leakage inductance. There must also be sufficient snubbing and damping to prevent the turn-off voltage on Pin 5 from ringing below ground. This will cause forward biasing of the substrate and can result in additional device power dissipation and converter instability. Suggested snubber and damper component values for Figures 24 and 26 are listed in the table above. The snubber and damper circuits will greatly reduce the radiated switching noise but there will be a slight penalty in converter efficiency. Figure 30. Recommended Printed Circuit Board Layout IC1 Feedback and VCC bias source. High switch current from transformer T1 to Power Switch Pin. R3 C5 High switch current return from Ground pin to negative terminal of capacitor C1. C4 R7 PB1 Feedback and VCC bias return to auxiliary winding ground terminal of transformer T1. In order to ensure proper device operation, the integrated circuit Ground, Pin 3, must connect as directly as possible to the printed circuit board ground foil. The ground pin should not be bent or offset by the board layout. The Power Switch circuit, Pin 5, can be offset if additional creepage distance is required using a TV suffix product. Components R3 and C5 connect through seperate and short copper traces to IC1. This will reduce the level of undesirable switching noise that appears on the Feedback Input and VCC pins. MOTOROLA ANALOG IC DEVICE DATA 19 MC33369 thru MC33374 Figure 31. Transformer Auxiliary Winding Elimination Zener Shunt Regulator Method + 10 k 4W IN965B - + + IC1 Figure 32. Transformer Auxiliary Winding Elimination Bipolar Transistor Series Regulator Method + 82 k 0.5 W IN965B 5.1 k 0.5 W + + MJE 13003 - IC1 20 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 Figure 33. Transformer Auxiliary Winding Elimination MOSFET Transistor Series Regulator Method + 510 k 0.1 W IN968B MTP 1N50E - + + IC1 Figures 31 through 33 show three possible methods of eliminating the transformer auxiliary winding and the associated fast recovery diode and capacitor. These methods are most practical for fixed or narrow range AC line voltage applications. Care must be taken when used in wide range AC line voltage applications, as the power dissipation in the voltage dropping elements may become excessive. The shunt regulator method is the most economical but the series pass methods dissipate less power when used in wide range line voltage applications. The MOSFET method is the most efficient since the gate requires essentially zero current. The component values shown in the above figures are for a nominal AC line voltage of 115 volts 20%. Figure 34. Converter Soft-Start VCC bias source IC1 PWM Feedback High switch current from transformer T1 to Power Switch Pin. 15 k R3 3.6 Q1 2N3906 Z1 1N757A 9.1 V 22 k Q2 2N3904 Z2 1N752A 5.6 V 47 k 1.5 k IN4148 Converter On/Off Control 0.01 10 k High switch current circuit return from Ground pin to negative terminal of capacitor C1. C5 47 33 k Converter soft-start can be implemented by separating the connection between Pins 1 and 2 with a resistor. Initially with the converter in the off state, the internal Start-Up circuit charges capacitor C5 to a voltage that exceeds the Vbe of Q1 plus the breakdown of Z1. This causes transistors Q1 and Q2 to latch on. Since the voltage at pin 2 is now greater than the internal shunt regulator threshold, minimum duty cycle pulses appear at the Power Switch circuit Pin 5. As the voltage across C5 approaches the regulation threshold, the PWM duty cycle will gradually increase until regulation is established at the converter output. Upon converter power down, the transistor latch will turn off at approximately 8.0 V which is slightly greater than the devices highest minimum operating voltage specification. This guarantees that soft-start will be active upon the next power-up cycle. MOTOROLA ANALOG IC DEVICE DATA 21 MC33369 thru MC33374 Figure 35. High Voltage Step-Up Converter L + + DC Input - MC 33374 Z1 Z2 3.3 k 100 10 + DC Input - Boost Rectifier + + 50 100 0.01 On/Off Toggle A simple transformerless high voltage step-up converter can be constructed with any of the devices in this series. The maximum output voltage of this topology is limited by the Power Switch circuit breakdown of 700 V minus the forward voltage drop of the boost rectifier. The converter requires a minimum input of 15 V to guarantee start-up. The regulated output voltage is equal to the sum of the zener voltage drops, plus the shunt regulator threshold, plus the voltage drop across the 3.3 k resistor. The boost rectifier must be a schottky or fast recovery type with sufficient current and voltage capability to meet the converter 's output requirements. Figure 36. Low Power Off-Line Converter 680* 92 to 276 VAC Input 680* 1N4006 - 1.0 nF *TRW flameproof fusable resistor MC 33370 1N4006 T1 1N4933 82 + + + 5.1 V/20 mA DC Output 10 100 MZP 4733A + 50 0.01 P4KE600 The converter shown above was designed for cost sensitive low power applications that require a line isolated power source. Typical applications include consumer and industrial equipment. Note that the transformer auxiliary winding has been eliminated and the MC33370 operates continuously in the auto restart mode. This method of converter operation is capable of providing an output power of up to 200 mW. 22 MOTOROLA ANALOG IC DEVICE DATA MC33369 thru MC33374 OUTLINE DIMENSIONS P SUFFIX PLASTIC PACKAGE CASE 626-05 ISSUE K 8 5 -B- 1 4 F NOTE 2 NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. DIM A B C D F G H J K L M N MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC --- 10_ 0.76 1.01 INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC --- 10_ 0.030 0.040 -A- L C -T- SEATING PLANE J N D K M M H G 0.13 (0.005) TA M B M T SUFFIX PLASTIC PACKAGE CASE 314D-04 ISSUE E -T- -Q- B C E SEATING PLANE NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION D DOES NOT INCLUDE INTERCONNECT BAR (DAMBAR) PROTRUSION. DIMENSION D INCLUDING PROTRUSION SHALL NOT EXCEED 10.92 (0.043) MAXIMUM. INCHES MIN MAX 0.572 0.613 0.390 0.415 0.170 0.180 0.025 0.038 0.048 0.055 0.067 BSC 0.087 0.112 0.015 0.025 0.990 1.045 0.320 0.365 0.140 0.153 0.105 0.117 MILLIMETERS MIN MAX 14.529 15.570 9.906 10.541 4.318 4.572 0.635 0.965 1.219 1.397 1.702 BSC 2.210 2.845 0.381 0.635 25.146 26.543 8.128 9.271 3.556 3.886 2.667 2.972 U K 12345 A L G D 5 PL J H M DIM A B C D E G H J K L Q U 0.356 (0.014) M TQ TV SUFFIX PLASTIC PACKAGE CASE 314E-01 ISSUE O B Q P OPTIONAL CHAMFER C E NOTES: 1. DIMENSIONS ARE IN INCHES. 2. INTERPRET DIMENSIONS AND TOLERANCES PER ASME Y14.5M, 1994. 3. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.005 TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. DIM A B C D E F G H J K L N Q S U V W INCHES MIN MAX 0.572 0.613 0.390 0.415 0.170 0.180 0.025 0.038 0.048 0.055 0.890 0.930 0.067 BSC 0.105 BSC 0.015 0.025 0.900 1.000 0.320 0.365 0.259 BSC 0.140 0.153 --- 0.620 0.468 0.505 --- 0.718 0.090 0.100 U K F 12345 A SL W V 5X G 5X 0.024 M J T N H T SEATING PLANE D TP M 0.010 M MOTOROLA ANALOG IC DEVICE DATA 23 MC33369 thru MC33374 SENSEFET is a trademark of Motorola, Inc. Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. "Typical" parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer. Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 1-303-675-2140 or 1-800-441-2447 Customer Focus Center: 1-800-521-6274 MfaxTM: RMFAX0@email.sps.mot.com - TOUCHTONE 1-602-244-6609 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, Motorola Fax Back System - US & Canada ONLY 1-800-774-1848 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852-26629298 - http://sps.motorola.com/mfax/ HOME PAGE: http://motorola.com/sps/ JAPAN: Nippon Motorola Ltd.; SPD, Strategic Planning Office, 141, 4-32-1 Nishi-Gotanda, Shinagawa-ku, Tokyo, Japan. 81-3-5487-8488 24 MC33370/D MOTOROLA ANALOG IC DEVICE DATA |
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